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RF COMMUNICATIONS PRODUCTS
SA624 High performance low power FM IF system with high-speed RSSI
Product specification Replaces data of November 3, 1992 RF Data Handbook 1997 Nov 07
Philips Semiconductors
Philips Semiconductors
Product specification
High performance low power FM IF system with high-speed RSSI
SA624
DESCRIPTION
The SA624 is pin-to-pin compatible with the SA604A, but has faster RSSI rise and fall time. The SA624 is an improved monolithic low-power FM IF system incorporating two limiting intermediate frequency amplifiers, quadrature detector, muting, logarithmic received signal strength indicator, and voltage regulator. The SA624 features higher IF bandwidth (25MHz) and temperature compensated RSSI and limiters permitting higher performance application compared with the SA604. The SA624 is available in 16-lead SO (surface-mounted miniature) package.
PIN CONFIGURATION
D Package
IF AMP DECOUPLING 1 GND 2 MUTE INPUT 3 VCC 4 16 IF AMP INPUT 15 IF AMP DECOUPLING 14 IF AMP OUTPUT 13 GND 12 LIMITER INPUT 11 LIMITER DECOUPLING 10 LIMITER DECOUPLING 9 LIMITER
RSSI OUTPUT 5 MUTE AUDIO OUTPUT 6
FEATURES
UNMUTE AUDIO OUTPUT 7 QUADRATURE INPUT 8
* Low power consumption: 3.4mA typical * Temperature compensated logarithmic Received Signal Strength
Indicator (RSSI) with a dynamic range in excess of 90dB
SR00440
* Fast RSSI rise and fall time * Two audio outputs - muted and unmuted * Low external component count; suitable for crystal/ceramic filters * Excellent sensitivity: 1.5V across input pins (0.22V into 50
matching network) for 12dB SINAD (Signal to Noise and Distortion ratio) at 455kHz
Figure 1. Pin Configuration
APPLICATIONS
* SA624 meets cellular radio specifications
* Digital cellular base station * Cellular radio FM IF * High performance communications receivers * Intermediate frequency amplification and detection up to 25MHz * RF level meter * Spectrum analyzer * Instrumentation * FSK and ASK data receivers
ORDERING INFORMATION
DESCRIPTION 16-Pin Plastic Small Outline (SO) package (Surface-mount) TEMPERATURE RANGE -40 to +85C ORDER CODE SA624D DWG # SOT109-1
ABSOLUTE MAXIMUM RATINGS
SYMBOL VCC TSTG TA JA Single supply voltage Storage temperature range Operating ambient temperature range SA624 Thermal impedance D package PARAMETER RATING 9 -65 to +150 -40 to +85 90 UNITS V C C C/W
1997 Nov 07
2
853-1647 18664
Philips Semiconductors
Product specification
High performance low power FM IF system with high-speed RSSI
SA624
BLOCK DIAGRAM
16 15 14 13
GND IF AMP LIMITER QUAD DET
12
11
10
9
LIMITER
SIGNAL STRENGTH VOLTAGE REGULATOR
MUTE
GND
VCC
1
2
3
4
5
6
7
8
SR00441
Figure 2. Block Diagram
DC ELECTRICAL CHARACTERISTICS
VCC = +6V, TA = 25C; unless otherwise stated. LIMITS SYMBOL PARAMETER TEST CONDITIONS MIN VCC ICC Power supply voltage range DC current drain Mute switch input threshold (ON) (OFF) 4.5 2.5 1.7 3.4 SA624 TYP MAX 8.0 4.2 1.0 V mA V V UNITS
1997 Nov 07
3
Philips Semiconductors
Product specification
High performance low power FM IF system with high-speed RSSI
SA624
AC ELECTRICAL CHARACTERISTICS
Typical reading at TA = 25C; VCC = +6V, unless otherwise stated. IF frequency = 455kHz; IF level = -47dBm; FM modulation = 1kHz with +8kHz peak deviation. Audio output with C-message weighted filter and de-emphasis capacitor. Test circuit Figure 3. The parameters listed below are tested using automatic test equipment to assure consistent electrical characterristics. The limits do not represent the ultimate performance limits of the device. Use of an optimized RF layout will improve many of the listed parameters. LIMITS SYMBOL PARAMETER TEST CONDITIONS MIN Input limiting -3dB AM rejection Recovered audio level Recovered audio level THD S/N Total harmonic distortion Signal-to-noise ratio No modulation for noise RF level = -118dBm RSSI output1 RF level = -68dBm RF level = -18dBm IF freq. = 455kHz IF level = -44dBm RSSI output rise time (10kHz pulse, no IF filter) IF level = -16dBm IF freq. = 10.7MHz IF level = -44dBm IF level = -16dBm IF freq. = 455kHz IF level = -44dBm RSSI output fall time (10kHz pulse, no IF filter) IF level = -16dBm IF freq. = 10.7MHz IF level = -44dBm IF level = -16dBm RSSI range RSSI accuracy IF input impedance IF output impedance Limiter input impedance Limiter output impedance Limiter output level no load Unmuted audio output resistance Muted audio output resistance R4 = 100k (Pin 5) R4 = 100k (Pin 5) 1.4 0.85 1.4 1.6 4.2 90 +1.5 1.6 1.0 1.6 300 280 58 58 s s dB dB k k k mVRMS k k 1.3 4.7 s s 1.2 1.1 s s 1.1 1.2 s s 0 1.9 4.0 Test at Pin 16 80% AM 1kHz 15nF de-emphasis 150pF de-emphasis -34 30 80 SA624 TYP -92 34 175 530 -42 73 160 2.65 4.85 650 3.1 5.6 260 MAX dBm/50 dB mVRMS mVRMS dB dB mV V V UNITS
NOTE: 1. SA604 data sheets refer to power at 50 input termination; about 21dB less power actually enters the internal 1.5k input. SA604 (50) SA624 (1.5k)/SA605 (1.5k -97dBm -118dBm -47dBm -68dBm +3dBm -18dBm
1997 Nov 07
4
Philips Semiconductors
Product specification
High performance low power FM IF system with high-speed RSSI
SA624
F1 NE624 TEST CIRCUIT C4 C1 INPUT R1 16 15 14 13 12 11 10 9 C7 SA624 C3 1 2 3 4 5 6 7 8 Q = 20 LOADED R2 C2 R3 C5 C6 F2
C8 S1 R4
C9 C10
C12
C11 RSSI OUTPUT
AUDIO OUTPUT
DATA OUTPUT
MUTE INPUT
VCC
C1 C2 C3 C4 C5 C6 C7 C8 C9 C10 C11 C12 F1 F2 R1 R2 R3 R4
100nF + 80 - 20% 63V K10000-25V Ceramic 100nF +10% 50V 100nF +10% 50V 100nF +10% 50V 100nF +10% 50V 10pF +2% 100V NPO Ceramic 100nF +10% 50V 100nF +10% 50V 15nF +10% 50V 150pF +2% 100V N1500 Ceramic 1nF +10% 100V K2000-Y5P Ceramic 6.8F +20% 25V Tantalum 455kHz Ceramic Filter Murata SFG455A3 455kHz (Ce = 180pF) TOKO RMC 2A6597H 51 +1% 1/4W Metal Film 1500 +1% 1/4W Metal Film 1500 +5% 1/8W Carbon Composition 100k +1% 1/4W Metal Film
SIGNETICS NE624 TEST CKT
GND OFF ON VCC GND GND
IF INPUT
M U T E RSSI AUDIO DATA
SIGNETICS NE624 TEST CKT
GND OFF ON VCC GND GND 1997 Nov 07
IF INPUT
M U T E RSSI AUDIO DATA
SR00442
Figure 3. SA624 Test Circuit
5
Philips Semiconductors
Product specification
High performance low power FM IF system with high-speed RSSI
SA624
16
15
14
13 GND
12
11
10
9
42k
42k
700
7k 1.6k 40k 700 35k FULL WAVE RECT. VOLTAGE/ CURRENT CONVERTER FULL WAVE RECT. 2k 4.5k 2k 8k 1.6k 40k
VEE VOLT REG VOLT REG
MUTE VCC
QUAD
DET BAND GAP VOLT 40k
40k
VCC 80k GND 1 2 3 VCC 4 5
55k
55k
80k
80k
6
7
8
SR00443
Figure 4. Equivalent Circuit
1997 Nov 07
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Philips Semiconductors
Product specification
High performance low power FM IF system with high-speed RSSI
SA624
0.5 to 1.3H
SFG455A3 1nF 22pF NE624 TEST CIRCUIT 44.545 3rd OVERTURE XTAL SFG455A3 6 5 16 15 14 13 12 11 0.1F 0.1F 455kHz Q=20 0.1F 10 9 0.1F SA602A 0.1F SA624
5.5H +6V 6.8F 100nF 10nF 8 7
5.6pF
10pF
1 47pF 0.21 to 0.28H 22pF
2
3
4
1
2
3
4
5
6
7
8
0.1F +6V VCC 100nF 10 AUDIO OUT - `C' MESSAGE WEIGHTED (0dB REF = RECOVERED AUDIO FOR +8kHz PEAK DEVIATION (dB) - -0 MUTE
100k
DATA OUT C-MSG FILTER AUDIO OUT
RSSI
NE624 IF INPUT (V) (1500) 100 1k 10k 100k AUDIO 4V RSSI (VOLTS)
-20 3V THD + NOISE
-40 2V AM (80% MOD) 1V NOISE -120 -100 -80 -60 -40 NE602 RF INPUT (dBm) (50) -20
-60
-80
SR00444
Figure 5. Typical Application Cellular Radio (45MHz to 455kHz)
CIRCUIT DESCRIPTION
The SA624 is a very high gain, high frequency device. Correct operation is not possible if good RF layout and gain stage practices are not used. The SA624 cannot be evaluated independent of circuit, components, and board layout. A physical layout which correlates to the electrical limits is shown in Figure 3. This configuration can be used as the basis for production layout. The SA624 is an IF signal processing system suitable for IF frequencies as high as 21.4MHz. The device consists of two limiting amplifiers, quadrature detector, direct audio output, muted audio output, and signal strength indicator (with output characteristic). The sub-systems are shown in Figure 4. A typical application with 45MHz input and 455kHz IF is shown in Figure 5.
One of the outputs is available at Pin 9 to drive an external quadrature capacitor and L/C quadrature tank. Both of the limiting amplifier stages are DC biased using feedback. The buffered output of the final differential amplifier is fed back to the input through 42k resistors. As shown in Figure 4, the input impedance is established for each stage by tapping one of the feedback resistors 1.6k from the input. This requires one additional decoupling capacitor from the tap point to ground.
42k V+ 15 16 1.6k 1 40k 7k
70014
IF Amplifiers
The IF amplifier section consists of two log-limiting stages. The first consists of two differential amplifiers with 39dB of gain and a small signal bandwidth of 41MHz (when driven from a 50 source). The output of the first limiter is a low impedance emitter follower with 1k of equivalent series resistance. The second limiting stage consists of three differential amplifiers with a gain of 62dB and a small signal AC bandwidth of 28MHz. The outputs of the final differential stage are buffered to the internal quadrature detector.
SR00445
Figure 6. First Limiter Bias Because of the very high gain, bandwidth and input impedance of the limiters, there is a very real potential for instability at IF frequencies above 455kHz. The basic phenomenon is shown in Figure 8. Distributed feedback (capacitance, inductance and radiated fields)
1997 Nov 07
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Philips Semiconductors
Product specification
High performance low power FM IF system with high-speed RSSI
SA624
42k
9
11 12
V+ 40k 8 BPF BPF 40k 80k
10
SR00446
SR00447
Figure 7. Second Limiter and Quadrature Detector
HIGH IMPEDANCE BPF
Figure 8. Feedback Paths
HIGH IMPEDANCE BPF
LOW IMPEDANCE
a. Terminating High Impedance Filters with Transformation to Low Impedance
BPF BPF A RESISTIVE LOSS INTO BPF 16 430 1
b. Low Impedance Termination and Gain Reduction Figure 9. Practical Termination
430
SR00448
15
14
13
12
11
10
9
NE 624
2
3
4
5
6
7
8
SR00449
Figure 10. Crystal Input Filter with Ceramic Interstage Filter forms a divider from the output of the limiters back to the inputs (including RF input). If this feedback divider does not cause attenuation greater than the gain of the forward path, then oscillation or low level regeneration is likely. If regeneration occurs, two symptoms may be present: (1)The RSSI output will be high with no signal input (should nominally be 250mV or lower), and (2) the demodulated output will demonstrate a threshold. Above a certain 1997 Nov 07 8 input level, the limited signal will begin to dominate the regeneration, and the demodulator will begin to operate in a "normal" manner. There are three primary ways to deal with regeneration: (1) Minimize the feedback by gain stage isolation, (2) lower the stage input impedances, thus increasing the feedback attenuation factor, and (3) reduce the gain. Gain reduction can effectively be
Philips Semiconductors
Product specification
High performance low power FM IF system with high-speed RSSI
SA624
accomplished by adding attenuation between stages. This can also lower the input impedance if well planned. Examples of impedance/gain adjustment are shown in Figure 9. Reduced gain will result in reduced limiting sensitivity. A feature of the SA624 IF amplifiers, which is not specified, is low phase shift. The SA624 is fabricated with a 10GHz process with very small collector capacitance. It is advantageous in some applications that the phase shift changes only a few degrees over a wide range of signal input amplitudes. Additional information will be provided in the upcoming product specification (this is a preliminary specification) when characterization is complete.
Quadrature Detector
Figure 7 shows an equivalent circuit of the SA624 quadrature detector. It is a multiplier cell similar to a mixer stage. Instead of mixing two different frequencies, it mixes two signals of common frequency but different phase. Internal to the device, a constant amplitude (limited) signal is differentially applied to the lower port of the multiplier. The same signal is applied single-ended to an external capacitor at Pin 9. There is a 90 phase shift across the plates of this capacitor, with the phase shifted signal applied to the upper port of the multiplier at Pin 8. A quadrature tank (parallel L/C network) permits frequency selective phase shifting at the IF frequency. This quadrature tank must be returned to ground through a DC blocking capacitor. The loaded Q of the quadrature tank impacts three fundamental aspects of the detector: Distortion, maximum modulated peak deviation, and audio output amplitude. Typical quadrature curves are illustrated in Figure 12. The phase angle translates to a shift in the multiplier output voltage. Thus a small deviation gives a large output with a high Q tank. However, as the deviation from resonance increases, the non-linearity of the curve increases (distortion), and, with too much deviation, the signal will be outside the quadrature region (limiting the peak deviation which can be demodulated). If the same peak deviation is applied to a lower Q tank, the deviation will remain in a region of the curve which is more linear (less distortion), but creates a smaller phase angle (smaller output amplitude). Thus the Q of the quadrature tank must be tailored to the design. Basic equations and an example for determining Q are shown below. This explanation includes first-order effects only.
Stability Considerations
The high gain and bandwidth of the SA624 in combination with its very low currents permit circuit implementation with superior performance. However, stability must be maintained and, to do that, every possible feedback mechanism must be addressed. These mechanisms are: 1) Supply lines and ground, 2) stray layout inductances and capacitances, 3) radiated fields, and 4) phase shift. As the system IF increases, so must the attention to fields and strays. However, ground and supply loops cannot be overlooked, especially at lower frequencies. Even at 455kHz, using the test layout in Figure 3, instability will occur if the supply line is not decoupled with two high quality RF capacitors, a 0.1F monolithic right at the VCC pin, and a 6.8F tantalum on the supply line. An electrolytic is not an adequate substitute. At 10.7MHz, a 1F tantalum has proven acceptable with this layout. Every layout must be evaluated on its own merit, but don't underestimate the importance of good supply bypass. At 455kHz, if the layout of Figure 3 or one substantially similar is used, it is possible to directly connect ceramic filters to the input and between limiter stages with no special consideration. At frequencies above 2MHz, some input impedance reduction is usually necessary. Figure 9 demonstrates a practical means. As illustrated in Figure 10, 430 external resistors are applied in parallel to the internal 1.6k load resistors, thus presenting approximately 330 to the filters. The input filter is a crystal type for narrowband selectivity. The filter is terminated with a tank which transforms to 330. The interstage filter is a ceramic type which doesn't contribute to system selectivity, but does suppress wideband noise and stray signal pickup. In wideband 10.7MHz IFs the input filter can also be ceramic, directly connected to Pin 16. In some products it may be impractical to utilize shielding, but this mechanism may be appropriate to 10.7MHz and 21.4MHz IF. One of the benefits of low current is lower radiated field strength, but lower does not mean non-existent. A spectrum analyzer with an active probe will clearly show IF energy with the probe held in the proximity of the second limiter output or quadrature coil. No specific recommendations are provided, but mechanical shielding should be considered if layout, bypass, and input impedance reduction do not solve a stubborn instability. The final stability consideration is phase shift. The phase shift of the limiters is very low, but there is phase shift contribution from the quadrature tank and the filters. Most filters demonstrate a large phase shift across their passband (especially at the edges). If the quadrature detector is tuned to the edge of the filter passband, the combined filter and quadrature phase shift can aggravate stability. This is not usually a problem, but should be kept in mind.
Frequency Discriminator Design Equations for SA624
VOUT
SR00450
Figure 11. CS CP + C S 1+ where 1 = 1 L(CP + CS) Q1 = R (CP + CS) 1 (1c) 1 1 Q1S + (1a) VIN
VO =
( S)
1
2
(1b)
From the above equation, the phase shift between nodes 1 and 2, or the phase across CS will be:
1997 Nov 07
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Philips Semiconductors
Product specification
High performance low power FM IF system with high-speed RSSI
1 = VO - VIN = tg-1 1- Figure 12 is the plot of vs. Q1 1 2
SA624
(2)
()
It is notable that at = 1, the phase shift is and the response is close to a straight 2 2Q1 = line with a slope of
( 1 )
resonances close, and to get maximum attenuation of higher harmonics at 455kHz IF, we have found that a CS = 10pF and CP = 164pF (commercial values of 150pF or 180pF may be practical), will give the best results. A variable inductor which can be adjusted around 0.7mH should be chosen and optimized for minimum distortion. (For 10.7MHz, a value of CS = 1pF is recommended.)
Audio Outputs
Two audio outputs are provided. Both are PNP current-to-voltage converters with 55k nominal internal loads. The unmuted output is always active to permit the use of signaling tones in systems such as cellular radio. The other output can be muted with 70dB typical attenuation. The two outputs have an internal 180 phase difference. The nominal frequency response of the audio outputs is 300kHz. this response can be increased with the addition of external resistors from the output pins to ground in parallel with the internal 55k resistors, thus lowering the output time constant. Singe the output structure is a current-to-voltage converter (current is driven into the resistance, creating a voltage drop), adding external parallel resistance also has the effect of lowering the output audio amplitude and DC level. This technique of audio bandwidth expansion can be effective in many applications such as SCA receivers and data transceivers. Because the two outputs have a 180 phase relationship, FSK demodulation can be accomplished by applying the two output differentially across the inputs of an op amp or comparator. Once the threshold of the reference frequency (or "no-signal" condition) has been established, the two outputs will shift in opposite directions (higher or lower output voltage) as the input frequency shifts. The output of the comparator will be logic output. The choice of op amp or comparator will depend on the data rate. With high IF frequency (10MHz and above), and wide IF bandwidth (L/C filters) data rates in excess of 4Mbaud are possible.
1
The signal VO would have a phase shift of - 2Q1 with respect to the V . IN 1 2 If VIN = A Sin t VO = A Sin (3)
t +
2
-
2Q1
1
Multiplying the two signals in the mixer, and low pass filtering yields: (4) VIN * VO = A2 Sin t Sin
t +
2
-
2Q1
1
after low pass filtering
VOUT =
12 A Cos 2
2
-
2Q1
1
(5)
= 1 A2 Sin 2Q1 2 1
(
)
(6)
VOUT 2Q1 For 2Q1
1 =
<<
2Q1
(
1 + 1 )
1
2
RSSI
The "received signal strength indicator", or RSSI, of the SA624 demonstrates monotonic logarithmic output over a range of 90dB. The signal strength output is derived from the summed stage currents in the limiting amplifiers. It is essentially independent of the IF frequency. Thus, unfiltered signals at the limiter inputs, spurious products, or regenerated signals will manifest themselves as RSSI outputs. An RSSI output of greater than 250mV with no signal (or a very small signal) applied, is an indication of possible regeneration or oscillation. In order to achieve optimum RSSI linearity, there must be a 12dB insertion loss between the first and second limiting amplifiers. With a typical 455kHz ceramic filter, there is a nominal 4dB insertion loss in the filter. An additional 6dB is lost in the interface between the filter and the input of the second limiter. A small amount of additional loss must be introduced with a typical ceramic filter. In the test circuit used for cellular radio applications (Figure 5) the optimum linearity was achieved with a 5.1k resistor from the output of the first limiter (Pin 14) to the input of the interstage filter. With this resistor from Pin 14 to the filter, sensitivity of 0.25V for 12dB SINAD was achieved. With the 3.6k resistor, sensitivity was optimized at 0.22V for 12dB SINAD with minor change in the RSSI linearity. Any application which requires optimized RSSI linearity, such as spectrum analyzers, cellular radio, and certain types of telemetry,
frequency from the carrier 1.
Which is discriminated FM output. (Note that is the deviation
Ref. Krauss, Raab, Bastian; Solid State Radio Eng.; Wiley, 1980, p. 311. Example: At 455kHz IF, with +5kHz FM deviation. The maximum normalized frequency will be 455 +5kHz = 1.010 or 0.990 455 Go to the f vs. normalized frequency curves (Figure 12) and draw a vertical straight line at
1 = 1.01.
The curves with Q = 100, Q = 40 are not linear, but Q = 20 and less shows better linearity for this application. Too small Q decreases the amplitude of the discriminated FM signal. (Eq. 6) Choose a Q = 20 The internal R of the 624 is 40k. From Eq. 1c, and then 1b, it results that CP + CS = 174pF and L = 0.7mH. A more exact analysis including the source resistance of the previous stage shows that there is a series and a parallel resonance in the phase detector tank. To make the parallel and series
1997 Nov 07
10
Philips Semiconductors
Product specification
High performance low power FM IF system with high-speed RSSI
SA624
will require careful attention to limiter interstage component selection. This will be especially true with high IF frequencies which require insertion loss or impedance reduction for stability. At low frequencies the RSSI makes an excellent logarithmic AC voltmeter. For data applications the RSSI is effective as an amplitude shift keyed (ASK) data slicer. If a comparator is applied to the RSSI and the threshold set slightly above the no signal level, when an in-band signal is received the comparator will be sliced. Unlike FSK demodulation, the maximum data rate is somewhat limited. An internal capacitor limits the RSSI frequency response to about
100kHz. At high data rates the rise and fall times will not be symmetrical. The RSSI output is a current-to-voltage converter similar to the audio outputs. However, an external resistor is required. With a 91k resistor, the output characteristic is 0.5V for a 10dB change in the input amplitude.
Additional Circuitry
Internal to the SA624 are voltage and current regulators which have been temperature compensated to maintain the performance of the device over a wide temperature range. These regulators are not accessible to the user.
200 175 Q = 80 Q = 60 150 Q = 20 125 Q = 10 100 Q = 100
75
50
25
0 0.95 0.975 1.0 1.025 1.05
SR00451
Figure 12. Phase vs Normalized IF Frequency 1
=1+ 1
1997 Nov 07
11
Philips Semiconductors
Product specification
High performance low power FM IF system with high-speed RSSI
SA624
2.0 1.9 1.8 RSSI FALL TIME ( s) 1.7 1.6 1.5 1.4 1.3 1.2 1.1 1.0 -40
RFINP-16dBm RFINP-44dBm RFINP-26dBm
-30
-20
-10
0
10
20
30
40
50
60
70
80
90
TEMPERATURE (C)
SR00452
Figure 13. SA624 Rise Time 455kHz IF Frequency
5.5 5.0 4.5 4.0 3.5 3.0 2.5 2.0 1.5 1.0 -40
RSSI FALL TIME ( s)
RFINP-16dBm RFINP-26dBm RFINP-44dBm
-30
-20
-10
0
10
20
30
40
50
60
70
80
90
TEMPERATURE (C)
SR00453
Figure 14. SA624 Fall Time 455kHz IF Frequency
1997 Nov 07
12
Philips Semiconductors
Product specification
High performance low power FM IF system with high-speed RSSI
SA624
3.0 2.8 2.6 RSSI FALL TIME ( s) 2.4 2.2 2.0 1.8 1.6 1.4 1.2 1.0 -40 -30 -20 -10 0 10 20 30 40 50 60 70 80 90
RFINP-26dBm RFINP-44dBm RFINP-16dBm
TEMPERATURE (C)
SR00455
Figure 15. SA624 Rise Time 10.7MHz IF Frequency
3.0 2.8 2.6 RSSI FALL TIME ( s) 2.4 2.2 2.0 1.8 1.6 1.4 1.2 1.0 -40 -30 -20 -10 0 10 20 30 40 50 60 70 80 90
RFINP-26dBm RFINP-44dBm RFINP-16dBm
TEMPERATURE (C)
SR00455
Figure 16. SA624 Fall Time 10.7MHz IF Frequency
1997 Nov 07
13
Philips Semiconductors
Product specification
High performance low power FM IF system with high-speed RSSI
SA624
SO16: plastic small outline package; 16 leads; body width 3.9 mm
SOT109-1
1997 Nov 07
14
Philips Semiconductors
Product specification
High performance low power FM IF system with high-speed RSSI
SA624
DEFINITIONS
Data Sheet Identification
Objective Specification
Product Status
Formative or in Design
Definition
This data sheet contains the design target or goal specifications for product development. Specifications may change in any manner without notice. This data sheet contains preliminary data, and supplementary data will be published at a later date. Philips Semiconductors reserves the right to make changes at any time without notice in order to improve design and supply the best possible product. This data sheet contains Final Specifications. Philips Semiconductors reserves the right to make changes at any time without notice, in order to improve design and supply the best possible product.
Preliminary Specification
Preproduction Product
Product Specification
Full Production
Philips Semiconductors and Philips Electronics North America Corporation reserve the right to make changes, without notice, in the products, including circuits, standard cells, and/or software, described or contained herein in order to improve design and/or performance. Philips Semiconductors assumes no responsibility or liability for the use of any of these products, conveys no license or title under any patent, copyright, or mask work right to these products, and makes no representations or warranties that these products are free from patent, copyright, or mask work right infringement, unless otherwise specified. Applications that are described herein for any of these products are for illustrative purposes only. Philips Semiconductors makes no representation or warranty that such applications will be suitable for the specified use without further testing or modification. LIFE SUPPORT APPLICATIONS Philips Semiconductors and Philips Electronics North America Corporation Products are not designed for use in life support appliances, devices, or systems where malfunction of a Philips Semiconductors and Philips Electronics North America Corporation Product can reasonably be expected to result in a personal injury. Philips Semiconductors and Philips Electronics North America Corporation customers using or selling Philips Semiconductors and Philips Electronics North America Corporation Products for use in such applications do so at their own risk and agree to fully indemnify Philips Semiconductors and Philips Electronics North America Corporation for any damages resulting from such improper use or sale. Philips Semiconductors 811 East Arques Avenue P.O. Box 3409 Sunnyvale, California 94088-3409 Telephone 800-234-7381 (c) Copyright Philips Electronics North America Corporation 1997 All rights reserved. Printed in U.S.A.
Philips Semiconductors
1997 Nov 07 15

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